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Definition of the Opus Audio Codec
RFC 6716

Document Type RFC - Proposed Standard (September 2012) Errata IPR
Updated by RFC 8251
Authors Jean-Marc Valin , Koen Vos , Timothy B. Terriberry
Last updated 2023-03-24
RFC stream Internet Engineering Task Force (IETF)
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IESG Responsible AD Robert Sparks
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RFC 6716
RFC 6716                 Interactive Audio Codec          September 2012

                       +-----------------+---+----+
                       | Frame size (ms) | 0 |  1 |
                       +-----------------+---+----+
                       |       2.5       | 0 | -1 |
                       |                 |   |    |
                       |        5        | 1 |  0 |
                       |                 |   |    |
                       |        10       | 2 |  0 |
                       |                 |   |    |
                       |        20       | 3 |  0 |
                       +-----------------+---+----+

       Table 62: TF Adjustments for Transient Frames and tf_select=0

                       +-----------------+---+----+
                       | Frame size (ms) | 0 |  1 |
                       +-----------------+---+----+
                       |       2.5       | 0 | -1 |
                       |                 |   |    |
                       |        5        | 1 | -1 |
                       |                 |   |    |
                       |        10       | 1 | -1 |
                       |                 |   |    |
                       |        20       | 1 | -1 |
                       +-----------------+---+----+

       Table 63: TF Adjustments for Transient Frames and tf_select=1

   A negative TF adjustment means that the temporal resolution is
   increased, while a positive TF adjustment means that the frequency
   resolution is increased.  Changes in TF resolution are implemented
   using the Hadamard transform [HADAMARD].  To increase the time
   resolution by N, N "levels" of the Hadamard transform are applied to
   the decoded vector for each interleaved MDCT vector.  To increase the
   frequency resolution (assumes a transient frame), then N levels of
   the Hadamard transform are applied _across_ the interleaved MDCT
   vector.  In the case of increased time resolution, the decoder uses
   the "sequency order" because the input vector is sorted in time.

4.3.5.  Anti-collapse Processing

   The anti-collapse feature is designed to avoid the situation where
   the use of multiple short MDCTs causes the energy in one or more of
   the MDCTs to be zero for some bands, causing unpleasant artifacts.
   When the frame has the transient bit set, an anti-collapse bit is
   decoded.  When anti-collapse is set, the energy in each small MDCT is
   prevented from collapsing to zero.  For each band of each MDCT where
   a collapse is detected, a pseudo-random signal is inserted with an

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   energy corresponding to the minimum energy over the two previous
   frames.  A renormalization step is then required to ensure that the
   anti-collapse step did not alter the energy preservation property.

4.3.6.  Denormalization

   Just as each band was normalized in the encoder, the last step of the
   decoder before the inverse MDCT is to denormalize the bands.  Each
   decoded normalized band is multiplied by the square root of the
   decoded energy.  This is done by denormalise_bands() (bands.c).

4.3.7.  Inverse MDCT

   The inverse MDCT implementation has no special characteristics.  The
   input is N frequency-domain samples and the output is 2*N time-domain
   samples, while scaling by 1/2.  A "low-overlap" window reduces the
   algorithmic delay.  It is derived from a basic (full-overlap) 240-
   sample version of the window used by the Vorbis codec:

                                                         2
                          /   /pi      /pi   n + 1/2\ \ \
                   W(n) = |sin|-- * sin|-- * -------| | |
                          \   \2       \2       L   / / /

   The low-overlap window is created by zero-padding the basic window
   and inserting ones in the middle, such that the resulting window
   still satisfies power complementarity [PRINCEN86].  The IMDCT and
   windowing are performed by mdct_backward (mdct.c).

4.3.7.1.  Post-Filter

   The output of the inverse MDCT (after weighted overlap-add) is sent
   to the post-filter.  Although the post-filter is applied at the end,
   the post-filter parameters are encoded at the beginning, just after
   the silence flag.  The post-filter can be switched on or off using
   one bit (logp=1).  If the post-filter is enabled, then the octave is
   decoded as an integer value between 0 and 6 of uniform probability.
   Once the octave is known, the fine pitch within the octave is decoded
   using 4+octave raw bits.  The final pitch period is equal to
   (16<<octave)+fine_pitch-1 so it is bounded between 15 and 1022,
   inclusively.  Next, the gain is decoded as three raw bits and is
   equal to G=3*(int_gain+1)/32.  The set of post-filter taps is decoded
   last, using a pdf equal to {2, 1, 1}/4.  Tapset zero corresponds to
   the filter coefficients g0 = 0.3066406250, g1 = 0.2170410156, g2 =
   0.1296386719.  Tapset one corresponds to the filter coefficients g0 =
   0.4638671875, g1 = 0.2680664062, g2 = 0, and tapset two uses filter
   coefficients g0 = 0.7998046875, g1 = 0.1000976562, g2 = 0.

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   The post-filter response is thus computed as:

             y(n) = x(n) + G*(g0*y(n-T) + g1*(y(n-T+1)+y(n-T+1))
                                        + g2*(y(n-T+2)+y(n-T+2)))

   During a transition between different gains, a smooth transition is
   calculated using the square of the MDCT window.  It is important that
   values of y(n) be interpolated one at a time such that the past value
   of y(n) used is interpolated.

4.3.7.2.  De-emphasis

   After the post-filter, the signal is de-emphasized using the inverse
   of the pre-emphasis filter used in the encoder:

                            1            1
                           ---- = ---------------
                           A(z)                -1
                                  1 - alpha_p*z

   where alpha_p=0.8500061035.

4.4.  Packet Loss Concealment (PLC)

   Packet Loss Concealment (PLC) is an optional decoder-side feature
   that SHOULD be included when receiving from an unreliable channel.
   Because PLC is not part of the bitstream, there are many acceptable
   ways to implement PLC with different complexity/quality trade-offs.

   The PLC in the reference implementation depends on the mode of last
   packet received.  In CELT mode, the PLC finds a periodicity in the
   decoded signal and repeats the windowed waveform using the pitch
   offset.  The windowed waveform is overlapped in such a way as to
   preserve the time-domain aliasing cancellation with the previous
   frame and the next frame.  This is implemented in celt_decode_lost()
   (mdct.c).  In SILK mode, the PLC uses LPC extrapolation from the
   previous frame, implemented in silk_PLC() (PLC.c).

4.4.1.  Clock Drift Compensation

   Clock drift refers to the gradual desynchronization of two endpoints
   whose sample clocks run at different frequencies while they are
   streaming live audio.  Differences in clock frequencies are generally
   attributable to manufacturing variation in the endpoints' clock
   hardware.  For long-lived streams, the time difference between sender
   and receiver can grow without bound.

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   When the sender's clock runs slower than the receiver's, the effect
   is similar to packet loss: too few packets are received.  The
   receiver can distinguish between drift and loss if the transport
   provides packet timestamps.  A receiver for live streams SHOULD
   conceal the effects of drift, and it MAY do so by invoking the PLC.

   When the sender's clock runs faster than the receiver's, too many
   packets will be received.  The receiver MAY respond by skipping any
   packet (i.e., not submitting the packet for decoding).  This is
   likely to produce a less severe artifact than if the frame were
   dropped after decoding.

   A decoder MAY employ a more sophisticated drift compensation method.
   For example, the NetEQ component [GOOGLE-NETEQ] of the Google WebRTC
   codebase [GOOGLE-WEBRTC] compensates for drift by adding or removing
   one period when the signal is highly periodic.  The reference
   implementation of Opus allows a caller to learn whether the current
   frame's signal is highly periodic, and if so what the period is,
   using the OPUS_GET_PITCH() request.

4.5.  Configuration Switching

   Switching between the Opus coding modes, audio bandwidths, and
   channel counts requires careful consideration to avoid audible
   glitches.  Switching between any two configurations of the CELT-only
   mode, any two configurations of the Hybrid mode, or from WB SILK to
   Hybrid mode does not require any special treatment in the decoder, as
   the MDCT overlap will smooth the transition.  Switching from Hybrid
   mode to WB SILK requires adding in the final contents of the CELT
   overlap buffer to the first SILK-only packet.  This can be done by
   decoding a 2.5 ms silence frame with the CELT decoder using the
   channel count of the SILK-only packet (and any choice of audio
   bandwidth), which will correctly handle the cases when the channel
   count changes as well.

   When changing the channel count for SILK-only or Hybrid packets, the
   encoder can avoid glitches by smoothly varying the stereo width of
   the input signal before or after the transition, and it SHOULD do so.
   However, other transitions between SILK-only packets or between NB or
   MB SILK and Hybrid packets may cause glitches, because neither the
   LSF coefficients nor the LTP, LPC, stereo unmixing, and resampler
   buffers are available at the new sample rate.  These switches SHOULD
   be delayed by the encoder until quiet periods or transients, where
   the inevitable glitches will be less audible.  Additionally, the
   bitstream MAY include redundant side information ("redundancy"), in
   the form of additional CELT frames embedded in each of the Opus
   frames around the transition.

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   The other transitions that cannot be easily handled are those where
   the lower frequencies switch between the SILK LP-based model and the
   CELT MDCT model.  However, an encoder may not have an opportunity to
   delay such a switch to a convenient point.  For example, if the
   content switches from speech to music, and the encoder does not have
   enough latency in its analysis to detect this in advance, there may
   be no convenient silence period during which to make the transition
   for quite some time.  To avoid or reduce glitches during these
   problematic mode transitions, and between audio bandwidth changes in
   the SILK-only modes, transitions MAY include redundant side
   information ("redundancy"), in the form of an additional CELT frame
   embedded in the Opus frame.

   A transition between coding the lower frequencies with the LP model
   and the MDCT model or a transition that involves changing the SILK
   bandwidth is only normatively specified when it includes redundancy.
   For those without redundancy, it is RECOMMENDED that the decoder use
   a concealment technique (e.g., make use of a PLC algorithm) to "fill
   in" the gap or discontinuity caused by the mode transition.
   Therefore, PLC MUST NOT be applied during any normative transition,
   i.e., when

   o  A packet includes redundancy for this transition (as described
      below),

   o  The transition is between any WB SILK packet and any Hybrid
      packet, or vice versa,

   o  The transition is between any two Hybrid mode packets, or

   o  The transition is between any two CELT mode packets,

   unless there is actual packet loss.

4.5.1.  Transition Side Information (Redundancy)

   Transitions with side information include an extra 5 ms "redundant"
   CELT frame within the Opus frame.  This frame is designed to fill in
   the gap or discontinuity in the different layers without requiring
   the decoder to conceal it.  For transitions from CELT-only to SILK-
   only or Hybrid, the redundant frame is inserted in the first Opus
   frame after the transition (i.e., the first SILK-only or Hybrid
   frame).  For transitions from SILK-only or Hybrid to CELT-only, the
   redundant frame is inserted in the last Opus frame before the
   transition (i.e., the last SILK-only or Hybrid frame).

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4.5.1.1.  Redundancy Flag

   The presence of redundancy is signaled in all SILK-only and Hybrid
   frames, not just those involved in a mode transition.  This allows
   the frames to be decoded correctly even if an adjacent frame is lost.
   For SILK-only frames, this signaling is implicit, based on the size
   of the Opus frame and the number of bits consumed decoding the SILK
   portion of it.  After decoding the SILK portion of the Opus frame,
   the decoder uses ec_tell() (see Section 4.1.6.1) to check if there
   are at least 17 bits remaining.  If so, then the frame contains
   redundancy.

   For Hybrid frames, this signaling is explicit.  After decoding the
   SILK portion of the Opus frame, the decoder uses ec_tell() (see
   Section 4.1.6.1) to ensure there are at least 37 bits remaining.  If
   so, it reads a symbol with the PDF in Table 64, and if the value is
   1, then the frame contains redundancy.  Otherwise (if there were
   fewer than 37 bits left or the value was 0), the frame does not
   contain redundancy.

                            +----------------+
                            | PDF            |
                            +----------------+
                            | {4095, 1}/4096 |
                            +----------------+

                       Table 64: Redundancy Flag PDF

4.5.1.2.  Redundancy Position Flag

   Since the current frame is a SILK-only or a Hybrid frame, it must be
   at least 10 ms.  Therefore, it needs an additional flag to indicate
   whether the redundant 5 ms CELT frame should be mixed into the
   beginning of the current frame, or the end.  After determining that a
   frame contains redundancy, the decoder reads a 1 bit symbol with a
   uniform PDF (Table 65).

                               +----------+
                               | PDF      |
                               +----------+
                               | {1, 1}/2 |
                               +----------+

                     Table 65: Redundancy Position PDF

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   If the value is zero, this is the first frame in the transition, and
   the redundancy belongs at the end.  If the value is one, this is the
   second frame in the transition, and the redundancy belongs at the
   beginning.  There is no way to specify that an Opus frame contains
   separate redundant CELT frames at both the beginning and the end.

4.5.1.3.  Redundancy Size

   Unlike the CELT portion of a Hybrid frame, the redundant CELT frame
   does not use the same entropy coder state as the rest of the Opus
   frame, because this would break the CELT bit allocation mechanism in
   Hybrid frames.  Thus, a redundant CELT frame always starts and ends
   on a byte boundary, even in SILK-only frames, where this is not
   strictly necessary.

   For SILK-only frames, the number of bytes in the redundant CELT frame
   is simply the number of whole bytes remaining, which must be at least
   2, due to the space check in Section 4.5.1.1.  For Hybrid frames, the
   number of bytes is equal to 2, plus a decoded unsigned integer less
   than 256 (see Section 4.1.5).  This may be more than the number of
   whole bytes remaining in the Opus frame, in which case the frame is
   invalid.  However, a decoder is not required to ignore the entire
   frame, as this may be the result of a bit error that desynchronized
   the range coder.  There may still be useful data before the error,
   and a decoder MAY keep any audio decoded so far instead of invoking
   the PLC, but it is RECOMMENDED that the decoder stop decoding and
   discard the rest of the current Opus frame.

   It would have been possible to avoid these invalid states in the
   design of Opus by limiting the range of the explicit length decoded
   from Hybrid frames by the actual number of whole bytes remaining.
   However, this would require an encoder to determine the rate
   allocation for the MDCT layer up front, before it began encoding that
   layer.  By allowing some invalid sizes, the encoder is able to defer
   that decision until much later.  When encoding Hybrid frames that do
   not include redundancy, the encoder must still decide up front if it
   wishes to use the minimum 37 bits required to trigger encoding of the
   redundancy flag, but this is a much looser restriction.

   After determining the size of the redundant CELT frame, the decoder
   reduces the size of the buffer currently in use by the range coder by
   that amount.  The MDCT layer reads any raw bits from the end of this
   reduced buffer, and all calculations of the number of bits remaining
   in the buffer must be done using this new, reduced size, rather than
   the original size of the Opus frame.

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4.5.1.4.  Decoding the Redundancy

   The redundant frame is decoded like any other CELT-only frame, with
   the exception that it does not contain a TOC byte.  The frame size is
   fixed at 5 ms, the channel count is set to that of the current frame,
   and the audio bandwidth is also set to that of the current frame,
   with the exception that for MB SILK frames, it is set to WB.

   If the redundancy belongs at the beginning (in a CELT-only to SILK-
   only or Hybrid transition), the final reconstructed output uses the
   first 2.5 ms of audio output by the decoder for the redundant frame
   as is, discarding the corresponding output from the SILK-only or
   Hybrid portion of the frame.  The remaining 2.5 ms is cross-lapped
   with the decoded SILK/Hybrid signal using the CELT's power-
   complementary MDCT window to ensure a smooth transition.

   If the redundancy belongs at the end (in a SILK-only or Hybrid to
   CELT-only transition), only the second half (2.5 ms) of the audio
   output by the decoder for the redundant frame is used.  In that case,
   the second half of the redundant frame is cross-lapped with the end
   of the SILK/Hybrid signal, again using CELT's power-complementary
   MDCT window to ensure a smooth transition.

4.5.2.  State Reset

   When a transition occurs, the state of the SILK or the CELT decoder
   (or both) may need to be reset before decoding a frame in the new
   mode.  This avoids reusing "out of date" memory, which may not have
   been updated in some time or may not be in a well-defined state due
   to, e.g., PLC.  The SILK state is reset before every SILK-only or
   Hybrid frame where the previous frame was CELT-only.  The CELT state
   is reset every time the operating mode changes and the new mode is
   either Hybrid or CELT-only, except when the transition uses
   redundancy as described above.  When switching from SILK-only or
   Hybrid to CELT-only with redundancy, the CELT state is reset before
   decoding the redundant CELT frame embedded in the SILK-only or Hybrid
   frame, but it is not reset before decoding the following CELT-only
   frame.  When switching from CELT-only mode to SILK-only or Hybrid
   mode with redundancy, the CELT decoder is not reset for decoding the
   redundant CELT frame.

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4.5.3.  Summary of Transitions

   Figure 18 illustrates all of the normative transitions involving a
   mode change, an audio bandwidth change, or both.  Each one uses an S,
   H, or C to represent an Opus frame in the corresponding mode.  In
   addition, an R indicates the presence of redundancy in the Opus frame
   with which it is cross-lapped.  Its location in the first or last
   5 ms is assumed to correspond to whether it is the frame before or
   after the transition.  Other uses of redundancy are non-normative.
   Finally, a c indicates the contents of the CELT overlap buffer after
   the previously decoded frame (i.e., as extracted by decoding a
   silence frame).

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    SILK to SILK with Redundancy:             S -> S -> S
                                                        &
                                                       !R -> R
                                                             &
                                                            ;S -> S -> S

    NB or MB SILK to Hybrid with Redundancy:  S -> S -> S
                                                        &
                                                       !R ->;H -> H -> H

    WB SILK to Hybrid:                        S -> S -> S ->!H -> H -> H

    SILK to CELT with Redundancy:             S -> S -> S
                                                        &
                                                       !R -> C -> C -> C

    Hybrid to NB or MB SILK with Redundancy:  H -> H -> H
                                                        &
                                                       !R -> R
                                                             &
                                                            ;S -> S -> S

    Hybrid to WB SILK:                        H -> H -> H -> c
                                                          \  +
                                                           > S -> S -> S

    Hybrid to CELT with Redundancy:           H -> H -> H
                                                        &
                                                       !R -> C -> C -> C

    CELT to SILK with Redundancy:             C -> C -> C -> R
                                                             &
                                                            ;S -> S -> S

    CELT to Hybrid with Redundancy:           C -> C -> C -> R
                                                             &
                                                            |H -> H -> H

    Key:
    S   SILK-only frame                 ;   SILK decoder reset
    H   Hybrid frame                    |   CELT and SILK decoder resets
    C   CELT-only frame                 !   CELT decoder reset
    c   CELT overlap                    +   Direct mixing
    R   Redundant CELT frame            &   Windowed cross-lap

                     Figure 18: Normative Transitions

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   The first two and the last two Opus frames in each example are
   illustrative, i.e., there is no requirement that a stream remain in
   the same configuration for three consecutive frames before or after a
   switch.

   The behavior of transitions without redundancy where PLC is allowed
   is non-normative.  An encoder might still wish to use these
   transitions if, for example, it doesn't want to add the extra bitrate
   required for redundancy or if it makes a decision to switch after it
   has already transmitted the frame that would have had to contain the
   redundancy.  Figure 19 illustrates the recommended cross-lapping and
   decoder resets for these transitions.

    SILK to SILK (audio bandwidth change):    S -> S -> S   ;S -> S -> S

    NB or MB SILK to Hybrid:                  S -> S -> S   |H -> H -> H

    SILK to CELT without Redundancy:          S -> S -> S -> P
                                                             &
                                                            !C -> C -> C

    Hybrid to NB or MB SILK:                  H -> H -> H -> c
                                                             +
                                                            ;S -> S -> S

    Hybrid to CELT without Redundancy:        H -> H -> H -> P
                                                             &
                                                            !C -> C -> C

    CELT to SILK without Redundancy:          C -> C -> C -> P
                                                             &
                                                            ;S -> S -> S

    CELT to Hybrid without Redundancy:        C -> C -> C -> P
                                                             &
                                                            |H -> H -> H

    Key:
    S   SILK-only frame                 ;   SILK decoder reset
    H   Hybrid frame                    |   CELT and SILK decoder resets
    C   CELT-only frame                 !   CELT decoder reset
    c   CELT overlap                    +   Direct mixing
    P   Packet Loss Concealment         &   Windowed cross-lap

             Figure 19: Recommended Non-Normative Transitions

   Encoders SHOULD NOT use other transitions, e.g., those that involve
   redundancy in ways not illustrated in Figure 18.

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5.  Opus Encoder

   Just like the decoder, the Opus encoder also normally consists of two
   main blocks: the SILK encoder and the CELT encoder.  However, unlike
   the case of the decoder, a valid (though potentially suboptimal) Opus
   encoder is not required to support all modes and may thus only
   include a SILK encoder module or a CELT encoder module.  The output
   bitstream of the Opus encoding contains bits from the SILK and CELT
   encoders, though these are not separable due to the use of a range
   coder.  A block diagram of the encoder is illustrated below.

                        +------------+    +---------+
                        |   Sample   |    |  SILK   |------+
                     +->|    Rate    |--->| Encoder |      V
      +-----------+  |  | Conversion |    |         | +---------+
      | Optional  |  |  +------------+    +---------+ |  Range  |
    ->| High-pass |--+                                | Encoder |---->
      |  Filter   |  |  +--------------+  +---------+ |         | Bit-
      +-----------+  |  |    Delay     |  |  CELT   | +---------+ stream
                     +->| Compensation |->| Encoder |      ^
                        |              |  |         |------+
                        +--------------+  +---------+

                          Figure 20: Opus Encoder

   For a normal encoder where both the SILK and the CELT modules are
   included, an optimal encoder should select which coding mode to use
   at run-time depending on the conditions.  In the reference
   implementation, the frame size is selected by the application, but
   the other configuration parameters (number of channels, bandwidth,
   mode) are automatically selected (unless explicitly overridden by the
   application) depending on the following:

   o  Requested bitrate

   o  Input sampling rate

   o  Type of signal (speech vs. music)

   o  Frame size in use

   The type of signal currently needs to be provided by the application
   (though it can be changed in real-time).  An Opus encoder
   implementation could also do automatic detection, but since Opus is
   an interactive codec, such an implementation would likely have to
   either delay the signal (for non-interactive applications) or delay
   the mode switching decisions (for interactive applications).

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   When the encoder is configured for voice over IP applications, the
   input signal is filtered by a high-pass filter to remove the lowest
   part of the spectrum that contains little speech energy and may
   contain background noise.  This is a second order Auto Regressive
   Moving Average (i.e., with poles and zeros) filter with a cut-off
   frequency around 50 Hz.  In the future, a music detector may also be
   used to lower the cut-off frequency when the input signal is detected
   to be music rather than speech.

5.1.  Range Encoder

   The range coder acts as the bit-packer for Opus.  It is used in three
   different ways: to encode

   o  Entropy-coded symbols with a fixed probability model using
      ec_encode() (entenc.c),

   o  Integers from 0 to (2**M - 1) using ec_enc_uint() or ec_enc_bits()
      (entenc.c),

   o  Integers from 0 to (ft - 1) (where ft is not a power of two) using
      ec_enc_uint() (entenc.c).

   The range encoder maintains an internal state vector composed of the
   four-tuple (val, rng, rem, ext) representing the low end of the
   current range, the size of the current range, a single buffered
   output byte, and a count of additional carry-propagating output
   bytes.  Both val and rng are 32-bit unsigned integer values, rem is a
   byte value or less than 255 or the special value -1, and ext is an
   unsigned integer with at least 11 bits.  This state vector is
   initialized at the start of each frame to the value
   (0, 2**31, -1, 0).  After encoding a sequence of symbols, the value
   of rng in the encoder should exactly match the value of rng in the
   decoder after decoding the same sequence of symbols.  This is a
   powerful tool for detecting errors in either an encoder or decoder
   implementation.  The value of val, on the other hand, represents
   different things in the encoder and decoder, and is not expected to
   match.

   The decoder has no analog for rem and ext.  These are used to perform
   carry propagation in the renormalization loop below.  Each iteration
   of this loop produces 9 bits of output, consisting of 8 data bits and
   a carry flag.  The encoder cannot determine the final value of the
   output bytes until it propagates these carry flags.  Therefore, the
   reference implementation buffers a single non-propagating output byte
   (i.e., one less than 255) in rem and keeps a count of additional

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   propagating (i.e., 255) output bytes in ext.  An implementation may
   choose to use any mathematically equivalent scheme to perform carry
   propagation.

5.1.1.  Encoding Symbols

   The main encoding function is ec_encode() (entenc.c), which encodes
   symbol k in the current context using the same three-tuple
   (fl[k], fh[k], ft) as the decoder to describe the range of the symbol
   (see Section 4.1).

   ec_encode() updates the state of the encoder as follows.  If fl[k] is
   greater than zero, then

                                       rng
                     val = val + rng - --- * (ft - fl)
                                       ft

                           rng
                     rng = --- * (fh - fl)
                           ft

   Otherwise, val is unchanged and

                                    rng
                        rng = rng - --- * (fh - fl)
                                    ft

   The divisions here are integer division.

5.1.1.1.  Renormalization

   After this update, the range is normalized using a procedure very
   similar to that of Section 4.1.2.1, implemented by ec_enc_normalize()
   (entenc.c).  The following process is repeated until rng > 2**23.
   First, the top 9 bits of val, (val>>23), are sent to the carry
   buffer, described in Section 5.1.1.2.  Then, the encoder sets

                        val = (val<<8) & 0x7FFFFFFF

                        rng = rng<<8

5.1.1.2.  Carry Propagation and Output Buffering

   The function ec_enc_carry_out() (entenc.c) implements carry
   propagation and output buffering.  It takes, as input, a 9-bit
   unsigned value, c, consisting of 8 data bits and an additional carry

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   bit.  If c is equal to the value 255, then ext is simply incremented,
   and no other state updates are performed.  Otherwise, let b = (c>>8)
   be the carry bit.  Then,

   o  If the buffered byte rem contains a value other than -1, the
      encoder outputs the byte (rem + b).  Otherwise, if rem is -1, no
      byte is output.

   o  If ext is non-zero, then the encoder outputs ext bytes -- all with
      a value of 0 if b is set, or 255 if b is unset -- and sets ext to
      0.

   o  rem is set to the 8 data bits:

                               rem = c & 255

5.1.2.  Alternate Encoding Methods

   The reference implementation uses three additional encoding methods
   that are exactly equivalent to the above, but make assumptions and
   simplifications that allow for a more efficient implementation.

5.1.2.1.  ec_encode_bin()

   The first is ec_encode_bin() (entenc.c), defined using the parameter
   ftb instead of ft.  It is mathematically equivalent to calling
   ec_encode() with ft = (1<<ftb), but it avoids using division.

5.1.2.2.  ec_enc_bit_logp()

   The next is ec_enc_bit_logp() (entenc.c), which encodes a single
   binary symbol.  The context is described by a single parameter, logp,
   which is the absolute value of the base-2 logarithm of the
   probability of a "1".  It is mathematically equivalent to calling
   ec_encode() with the 3-tuple (fl[k] = 0, fh[k] = (1<<logp) - 1,
   ft = (1<<logp)) if k is 0 and with (fl[k] = (1<<logp) - 1,
   fh[k] = ft = (1<<logp)) if k is 1.  The implementation requires no
   multiplications or divisions.

5.1.2.3.  ec_enc_icdf()

   The last is ec_enc_icdf() (entenc.c), which encodes a single binary
   symbol with a table-based context of up to 8 bits.  This uses the
   same icdf table as ec_dec_icdf() from Section 4.1.3.3.  The function

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   is mathematically equivalent to calling ec_encode() with
   fl[k] = (1<<ftb) - icdf[k-1] (or 0 if k == 0), fh[k] = (1<<ftb) -
    icdf[k], and ft = (1<<ftb).  This only saves a few arithmetic
   operations over ec_encode_bin(), but it allows the encoder to use the
   same icdf tables as the decoder.

5.1.3.  Encoding Raw Bits

   The raw bits used by the CELT layer are packed at the end of the
   buffer using ec_enc_bits() (entenc.c).  Because the raw bits may
   continue into the last byte output by the range coder if there is
   room in the low-order bits, the encoder must be prepared to merge
   these values into a single byte.  The procedure in Section 5.1.5 does
   this in a way that ensures both the range coded data and the raw bits
   can be decoded successfully.

5.1.4.  Encoding Uniformly Distributed Integers

   The function ec_enc_uint() (entenc.c) encodes one of ft equiprobable
   symbols in the range 0 to (ft - 1), inclusive, each with a frequency
   of 1, where ft may be as large as (2**32 - 1).  Like the decoder (see
   Section 4.1.5), it splits up the value into a range coded symbol
   representing up to 8 of the high bits, and, if necessary, raw bits
   representing the remainder of the value.

   ec_enc_uint() takes a two-tuple (t, ft), where t is the unsigned
   integer to be encoded, 0 <= t < ft, and ft is not necessarily a power
   of two.  Let ftb = ilog(ft - 1), i.e., the number of bits required to
   store (ft - 1) in two's complement notation.  If ftb is 8 or less,
   then t is encoded directly using ec_encode() with the three-tuple (t,
   t + 1, ft).

   If ftb is greater than 8, then the top 8 bits of t are encoded using
   the three-tuple (t>>(ftb - 8), (t>>(ftb - 8)) + 1,
   ((ft - 1)>>(ftb - 8)) + 1), and the remaining bits,
   (t & ((1<<(ftb - 8)) - 1), are encoded as raw bits with
   ec_enc_bits().

5.1.5.  Finalizing the Stream

   After all symbols are encoded, the stream must be finalized by
   outputting a value inside the current range.  Let end be the unsigned
   integer in the interval [val, val + rng) with the largest number of
   trailing zero bits, b, such that (end + (1<<b) - 1) is also in the
   interval [val, val + rng).  This choice of end allows the maximum
   number of trailing bits to be set to arbitrary values while still
   ensuring the range coded part of the buffer can be decoded correctly.

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   Then, while end is not zero, the top 9 bits of end, i.e., (end>>23),
   are passed to the carry buffer in accordance with the procedure in
   Section 5.1.1.2, and end is updated via

                        end = (end<<8) & 0x7FFFFFFF

   Finally, if the buffered output byte, rem, is neither zero nor the
   special value -1, or the carry count, ext, is greater than zero, then
   9 zero bits are sent to the carry buffer to flush it to the output
   buffer.  When outputting the final byte from the range coder, if it
   would overlap any raw bits already packed into the end of the output
   buffer, they should be ORed into the same byte.  The bit allocation
   routines in the CELT layer should ensure that this can be done
   without corrupting the range coder data so long as end is chosen as
   described above.  If there is any space between the end of the range
   coder data and the end of the raw bits, it is padded with zero bits.
   This entire process is implemented by ec_enc_done() (entenc.c).

5.1.6.  Current Bit Usage

   The bit allocation routines in Opus need to be able to determine a
   conservative upper bound on the number of bits that have been used to
   encode the current frame thus far.  This drives allocation decisions
   and ensures that the range coder and raw bits will not overflow the
   output buffer.  This is computed in the reference implementation to
   whole-bit precision by the function ec_tell() (entcode.h) and to
   fractional 1/8th bit precision by the function ec_tell_frac()
   (entcode.c).  Like all operations in the range coder, it must be
   implemented in a bit-exact manner, and it must produce exactly the
   same value returned by the same functions in the decoder after
   decoding the same symbols.

5.2.  SILK Encoder

   In many respects, the SILK encoder mirrors the SILK decoder described
   in Section 4.2.  Details such as the quantization and range coder
   tables can be found there, while this section describes the high-
   level design choices that were made.  The diagram below shows the
   basic modules of the SILK encoder.

               +----------+    +--------+    +---------+
               |  Sample  |    | Stereo |    |  SILK   |
        ------>|   Rate   |--->| Mixing |--->|  Core   |---------->
        Input  |Conversion|    |        |    | Encoder |  Bitstream
               +----------+    +--------+    +---------+

                          Figure 21: SILK Encoder

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5.2.1.  Sample Rate Conversion

   The input signal's sampling rate is adjusted by a sample rate
   conversion module so that it matches the SILK internal sampling rate.
   The input to the sample rate converter is delayed by a number of
   samples depending on the sample rate ratio, such that the overall
   delay is constant for all input and output sample rates.

5.2.2.  Stereo Mixing

   The stereo mixer is only used for stereo input signals.  It converts
   a stereo left-right signal into an adaptive mid-side representation.
   The first step is to compute non-adaptive mid-side signals as half
   the sum and difference between left and right signals.  The side
   signal is then minimized in energy by subtracting a prediction of it
   based on the mid signal.  This prediction works well when the left
   and right signals exhibit linear dependency, for instance, for an
   amplitude-panned input signal.  Like in the decoder, the prediction
   coefficients are linearly interpolated during the first 8 ms of the
   frame.  The mid signal is always encoded, whereas the residual side
   signal is only encoded if it has sufficient energy compared to the
   mid signal's energy.  If it has not, the "mid_only_flag" is set
   without encoding the side signal.

   The predictor coefficients are coded regardless of whether the side
   signal is encoded.  For each frame, two predictor coefficients are
   computed, one that predicts between low-passed mid and side channels,
   and one that predicts between high-passed mid and side channels.  The
   low-pass filter is a simple three-tap filter and creates a delay of
   one sample.  The high-pass filtered signal is the difference between
   the mid signal delayed by one sample and the low-passed signal.
   Instead of explicitly computing the high-passed signal, it is
   computationally more efficient to transform the prediction
   coefficients before applying them to the filtered mid signal, as
   follows:

               pred(n) = LP(n) * w0 + HP(n) * w1
                       = LP(n) * w0 + (mid(n-1) - LP(n)) * w1
                       = LP(n) * (w0 - w1) + mid(n-1) * w1

   where w0 and w1 are the low-pass and high-pass prediction
   coefficients, mid(n-1) is the mid signal delayed by one sample, LP(n)
   and HP(n) are the low-passed and high-passed signals and pred(n) is
   the prediction signal that is subtracted from the side signal.

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5.2.3.  SILK Core Encoder

   What follows is a description of the core encoder and its components.
   For simplicity, the core encoder is referred to simply as the encoder
   in the remainder of this section.  An overview of the encoder is
   given in Figure 22.

                                                                +---+
                             +--------------------------------->|   |
        +---------+          |      +---------+                 |   |
        |Voice    |          |      |LTP      |12               |   |
    +-->|Activity |--+       +----->|Scaling  |-----------+---->|   |
    |   |Detection|3 |       |      |Control  |<--+       |     |   |
    |   +---------+  |       |      +---------+   |       |     |   |
    |                |       |      +---------+   |       |     |   |
    |                |       |      |Gains    |   |       |     |   |
    |                |       |  +-->|Processor|---|---+---|---->| R |
    |                |       |  |   |         |11 |   |   |     | a |
    |               \/       |  |   +---------+   |   |   |     | n |
    |          +---------+   |  |   +---------+   |   |   |     | g |
    |          |Pitch    |   |  |   |LSF      |   |   |   |     | e |
    |       +->|Analysis |---+  |   |Quantizer|---|---|---|---->|   |
    |       |  |         |4  |  |   |         |8  |   |   |     | E |-->
    |       |  +---------+   |  |   +---------+   |   |   |     | n | 2
    |       |                |  |    9/\  10|     |   |   |     | c |
    |       |                |  |     |    \/     |   |   |     | o |
    |       |  +---------+   |  |   +----------+  |   |   |     | d |
    |       |  |Noise    |   +--|-->|Prediction|--+---|---|---->| e |
    |       +->|Shaping  |---|--+   |Analysis  |7 |   |   |     | r |
    |       |  |Analysis |5  |  |   |          |  |   |   |     |   |
    |       |  +---------+   |  |   +----------+  |   |   |     |   |
    |       |                |  |        /\       |   |   |     |   |
    |       |     +----------|--|--------+        |   |   |     |   |
    |       |     |         \/  \/               \/  \/  \/     |   |
    |       |     |      +----------+          +------------+   |   |
    |       |     |      |          |          |Noise       |   |   |
   -+-------+-----+----->|Pre-filter|--------->|Shaping     |-->|   |
   1                     |          | 6        |Quantization|13 |   |
                         +----------+          +------------+   +---+

   1:  Input speech signal
   2:  Range encoded bitstream
   3:  Voice activity estimate
   4:  Pitch lags (per 5 ms) and voicing decision (per 20 ms)
   5:  Noise shaping quantization coefficients
     - Short-term synthesis and analysis
       noise shaping coefficients (per 5 ms)

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     - Long-term synthesis and analysis noise
       shaping coefficients (per 5 ms and for voiced speech only)
     - Noise shaping tilt (per 5 ms)
     - Quantizer gain/step size (per 5 ms)
   6:  Input signal filtered with analysis noise shaping filters
   7:  Short- and Long-Term Prediction coefficients
       LTP (per 5 ms) and LPC (per 20 ms)
   8:  LSF quantization indices
   9:  LSF coefficients
   10: Quantized LSF coefficients
   11: Processed gains, and synthesis noise shape coefficients
   12: LTP state scaling coefficient.  Controlling error
       propagation / prediction gain trade-off
   13: Quantized signal

                       Figure 22: SILK Core Encoder

5.2.3.1.  Voice Activity Detection

   The input signal is processed by a Voice Activity Detection (VAD)
   algorithm to produce a measure of voice activity, spectral tilt, and
   signal-to-noise estimates for each frame.  The VAD uses a sequence of
   half-band filterbanks to split the signal into four subbands:
   0...Fs/16, Fs/16...Fs/8, Fs/8...Fs/4, and Fs/4...Fs/2, where Fs is
   the sampling frequency (8, 12, 16, or 24 kHz).  The lowest subband,
   from 0 - Fs/16, is high-pass filtered with a first-order moving
   average (MA) filter (with transfer function H(z) = 1-z**(-1)) to
   reduce the energy at the lowest frequencies.  For each frame, the
   signal energy per subband is computed.  In each subband, a noise
   level estimator tracks the background noise level and a Signal-to-
   Noise Ratio (SNR) value is computed as the logarithm of the ratio of
   energy-to-noise level.  Using these intermediate variables, the
   following parameters are calculated for use in other SILK modules:

   o  Average SNR.  The average of the subband SNR values.

   o  Smoothed subband SNRs.  Temporally smoothed subband SNR values.

   o  Speech activity level.  Based on the average SNR and a weighted
      average of the subband energies.

   o  Spectral tilt.  A weighted average of the subband SNRs, with
      positive weights for the low subbands and negative weights for the
      high subbands.

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5.2.3.2.  Pitch Analysis

   The input signal is processed by the open loop pitch estimator shown
   in Figure 23.

                                    +--------+  +----------+
                                    |2 x Down|  |Time-     |
                                 +->|sampling|->|Correlator|     |
                                 |  |        |  |          |     |4
                                 |  +--------+  +----------+    \/
                                 |                    | 2    +-------+
                                 |                    |  +-->|Speech |5
       +---------+    +--------+ |                   \/  |   |Type   |->
       |LPC      |    |Down    | |              +----------+ |       |
    +->|Analysis | +->|sample  |-+------------->|Time-     | +-------+
    |  |         | |  |to 8 kHz|                |Correlator|----------->
    |  +---------+ |  +--------+                |__________|          6
    |       |      |                                  |3
    |      \/      |                                 \/
    |  +---------+ |                            +----------+
    |  |Whitening| |                            |Time-     |
   -+->|Filter   |-+--------------------------->|Correlator|----------->
   1   |         |                              |          |          7
       +---------+                              +----------+

   1: Input signal
   2: Lag candidates from stage 1
   3: Lag candidates from stage 2
   4: Correlation threshold
   5: Voiced/unvoiced flag
   6: Pitch correlation
   7: Pitch lags

              Figure 23: Block Diagram of the Pitch Estimator

   The pitch analysis finds a binary voiced/unvoiced classification,
   and, for frames classified as voiced, four pitch lags per frame --
   one for each 5 ms subframe -- and a pitch correlation indicating the
   periodicity of the signal.  The input is first whitened using a
   Linear Prediction (LP) whitening filter, where the coefficients are
   computed through standard Linear Predictive Coding (LPC) analysis.
   The order of the whitening filter is 16 for best results, but is
   reduced to 12 for medium complexity and 8 for low complexity modes.
   The whitened signal is analyzed to find pitch lags for which the time
   correlation is high.  The analysis consists of three stages for
   reducing the complexity:

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   o  In the first stage, the whitened signal is downsampled to 4 kHz
      (from 8 kHz), and the current frame is correlated to a signal
      delayed by a range of lags, starting from a shortest lag
      corresponding to 500 Hz, to a longest lag corresponding to 56 Hz.

   o  The second stage operates on an 8 kHz signal (downsampled from 12,
      16, or 24 kHz) and measures time correlations only near the lags
      corresponding to those that had sufficiently high correlations in
      the first stage.  The resulting correlations are adjusted for a
      small bias towards short lags to avoid ending up with a multiple
      of the true pitch lag.  The highest adjusted correlation is
      compared to a threshold depending on:

      *  Whether the previous frame was classified as voiced.

      *  The speech activity level.

      *  The spectral tilt.

      If the threshold is exceeded, the current frame is classified as
      voiced and the lag with the highest adjusted correlation is stored
      for a final pitch analysis of the highest precision in the third
      stage.

   o  The last stage operates directly on the whitened input signal to
      compute time correlations for each of the four subframes
      independently in a narrow range around the lag with highest
      correlation from the second stage.

5.2.3.3.  Noise Shaping Analysis

   The noise shaping analysis finds gains and filter coefficients used
   in the pre-filter and noise shaping quantizer.  These parameters are
   chosen such that they will fulfill several requirements:

   o  Balancing quantization noise and bitrate.  The quantization gains
      determine the step size between reconstruction levels of the
      excitation signal.  Therefore, increasing the quantization gain
      amplifies quantization noise, but also reduces the bitrate by
      lowering the entropy of the quantization indices.

   o  Spectral shaping of the quantization noise; the noise shaping
      quantizer is capable of reducing quantization noise in some parts
      of the spectrum at the cost of increased noise in other parts
      without substantially changing the bitrate.  By shaping the noise
      such that it follows the signal spectrum, it becomes less audible.
      In practice, best results are obtained by making the shape of the
      noise spectrum slightly flatter than the signal spectrum.

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   o  De-emphasizing spectral valleys; by using different coefficients
      in the analysis and synthesis part of the pre-filter and noise
      shaping quantizer, the levels of the spectral valleys can be
      decreased relative to the levels of the spectral peaks such as
      speech formants and harmonics.  This reduces the entropy of the
      signal, which is the difference between the coded signal and the
      quantization noise, thus lowering the bitrate.

   o  Matching the levels of the decoded speech formants to the levels
      of the original speech formants; an adjustment gain and a first
      order tilt coefficient are computed to compensate for the effect
      of the noise shaping quantization on the level and spectral tilt.

                 / \   ___
                  |   // \\
                  |  //   \\     ____
                  |_//     \\___//  \\         ____
                  | /  ___  \   /    \\       //  \\
                P |/  /   \  \_/      \\_____//    \\
                o |  /     \     ____  \     /      \\
                w | /       \___/    \  \___/  ____  \\___ 1
                e |/                  \       /    \  \
                r |                    \_____/      \  \__ 2
                  |                                  \
                  |                                   \___ 3
                  |
                  +---------------------------------------->
                                   Frequency

               1: Input signal spectrum
               2: De-emphasized and level matched spectrum
               3: Quantization noise spectrum

      Figure 24: Noise Shaping and Spectral De-emphasis Illustration

   Figure 24 shows an example of an input signal spectrum (1).  After
   de-emphasis and level matching, the spectrum has deeper valleys (2).
   The quantization noise spectrum (3) more or less follows the input
   signal spectrum, while having slightly less pronounced peaks.  The
   entropy, which provides a lower bound on the bitrate for encoding the
   excitation signal, is proportional to the area between the de-
   emphasized spectrum (2) and the quantization noise spectrum (3).
   Without de-emphasis, the entropy is proportional to the area between
   input spectrum (1) and quantization noise (3) -- clearly higher.

   The transformation from input signal to de-emphasized signal can be
   described as a filtering operation with a filter

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                                             -1    Wana(z)
                  H(z) = G * ( 1 - c_tilt * z  ) * -------
                                                   Wsyn(z)

   having an adjustment gain G, a first order tilt adjustment filter
   with tilt coefficient c_tilt, and where

                       16                           d
                       __            -k        -L  __            -k
        Wana(z) = (1 - \ a_ana(k) * z  )*(1 - z  * \ b_ana(k) * z  )
                       /_                          /_
                       k=1                         k=-d

   is the analysis part of the de-emphasis filter, consisting of the
   short-term shaping filter with coefficients a_ana(k) and the long-
   term shaping filter with coefficients b_ana(k) and pitch lag L.  The
   parameter d determines the number of long-term shaping filter taps.

   Similarly, but without the tilt adjustment, the synthesis part can be
   written as

                       16                           d
                       __            -k        -L  __            -k
        Wsyn(z) = (1 - \ a_syn(k) * z  )*(1 - z  * \ b_syn(k) * z  )
                       /_                          /_
                       k=1                         k=-d

   All noise shaping parameters are computed and applied per subframe of
   5 ms.  First, an LPC analysis is performed on a windowed signal block
   of 15 ms.  The signal block has a look-ahead of 5 ms relative to the
   current subframe, and the window is an asymmetric sine window.  The
   LPC analysis is done with the autocorrelation method, with an order
   of between 8, in lowest-complexity mode, and 16, for best quality.

   Optionally, the LPC analysis and noise shaping filters are warped by
   replacing the delay elements by first-order allpass filters.  This
   increases the frequency resolution at low frequencies and reduces it
   at high ones, which better matches the human auditory system and
   improves quality.  The warped analysis and filtering comes at a cost
   in complexity and is therefore only done in higher complexity modes.

   The quantization gain is found by taking the square root of the
   residual energy from the LPC analysis and multiplying it by a value
   inversely proportional to the coding quality control parameter and
   the pitch correlation.

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   Next, the two sets of short-term noise shaping coefficients a_ana(k)
   and a_syn(k) are obtained by applying different amounts of bandwidth
   expansion to the coefficients found in the LPC analysis.  This
   bandwidth expansion moves the roots of the LPC polynomial towards the
   origin, using the formulas

                                              k
                         a_ana(k) = a(k)*g_ana   and

                                              k
                         a_syn(k) = a(k)*g_syn

   where a(k) is the k'th LPC coefficient, and the bandwidth expansion
   factors g_ana and g_syn are calculated as

                         g_ana = 0.95 - 0.01*C  and

                         g_syn = 0.95 + 0.01*C

   where C is the coding quality control parameter between 0 and 1.
   Applying more bandwidth expansion to the analysis part than to the
   synthesis part gives the desired de-emphasis of spectral valleys in
   between formants.

   The long-term shaping is applied only during voiced frames.  It uses
   a three-tap filter, described by

                   b_ana = F_ana * [0.25, 0.5, 0.25]  and

                   b_syn = F_syn * [0.25, 0.5, 0.25].

   For unvoiced frames, these coefficients are set to 0.  The
   multiplication factors F_ana and F_syn are chosen between 0 and 1,
   depending on the coding quality control parameter, as well as the
   calculated pitch correlation and smoothed subband SNR of the lowest
   subband.  By having F_ana less than F_syn, the pitch harmonics are
   emphasized relative to the valleys in between the harmonics.

   The tilt coefficient c_tilt is for unvoiced frames chosen as

                               c_tilt = 0.25

   and as

                         c_tilt = 0.25 + 0.2625 * V

   for voiced frames, where V is the voice activity level between 0 and
   1.

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   The adjustment gain G serves to correct any level mismatch between
   the original and decoded signals that might arise from the noise
   shaping and de-emphasis.  This gain is computed as the ratio of the
   prediction gain of the short-term analysis and synthesis filter
   coefficients.  The prediction gain of an LPC synthesis filter is the
   square root of the output energy when the filter is excited by a
   unit-energy impulse on the input.  An efficient way to compute the
   prediction gain is by first computing the reflection coefficients
   from the LPC coefficients through the step-down algorithm, and
   extracting the prediction gain from the reflection coefficients as

                                    K
                                   ___          2  -0.5
                      predGain = ( | | 1 - (r_k)  )
                                   k=1

   where r_k is the k'th reflection coefficient.

   Initial values for the quantization gains are computed as the square
   root of the residual energy of the LPC analysis, adjusted by the
   coding quality control parameter.  These quantization gains are later
   adjusted based on the results of the prediction analysis.

5.2.3.4.  Prediction Analysis

   The prediction analysis is performed in one of two ways depending on
   how the pitch estimator classified the frame.  The processing for
   voiced and unvoiced speech is described in Section 5.2.3.4.1 and
   Section 5.2.3.4.2, respectively.  Inputs to this function include the
   pre-whitened signal from the pitch estimator (see Section 5.2.3.2).

5.2.3.4.1.  Voiced Speech

   For a frame of voiced speech, the pitch pulses will remain dominant
   in the pre-whitened input signal.  Further whitening is desirable as
   it leads to higher quality at the same available bitrate.  To achieve
   this, a Long-Term Prediction (LTP) analysis is carried out to
   estimate the coefficients of a fifth-order LTP filter for each of
   four subframes.  The LTP coefficients are quantized using the method
   described in Section 5.2.3.6, and the quantized LTP coefficients are
   used to compute the LTP residual signal.  This LTP residual signal is
   the input to an LPC analysis where the LPC coefficients are estimated
   using Burg's method [BURG], such that the residual energy is
   minimized.  The estimated LPC coefficients are converted to a Line
   Spectral Frequency (LSF) vector and quantized as described in
   Section 5.2.3.5.  After quantization, the quantized LSF vector is
   converted back to LPC coefficients using the full procedure in
   Section 4.2.7.5.  By using quantized LTP coefficients and LPC

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   coefficients derived from the quantized LSF coefficients, the encoder
   remains fully synchronized with the decoder.  The quantized LPC and
   LTP coefficients are also used to filter the input signal and measure
   residual energy for each of the four subframes.

5.2.3.4.2.  Unvoiced Speech

   For a speech signal that has been classified as unvoiced, there is no
   need for LTP filtering, as it has already been determined that the
   pre-whitened input signal is not periodic enough within the allowed
   pitch period range for LTP analysis to be worth the cost in terms of
   complexity and bitrate.  The pre-whitened input signal is therefore
   discarded, and, instead, the input signal is used for LPC analysis
   using Burg's method.  The resulting LPC coefficients are converted to
   an LSF vector and quantized as described in the following section.
   They are then transformed back to obtain quantized LPC coefficients,
   which are then used to filter the input signal and measure residual
   energy for each of the four subframes.

5.2.3.4.2.1.  Burg's Method

   The main purpose of linear prediction in SILK is to reduce the
   bitrate by minimizing the residual energy.  At least at high
   bitrates, perceptual aspects are handled independently by the noise
   shaping filter.  Burg's method is used because it provides higher
   prediction gain than the autocorrelation method and, unlike the
   covariance method, produces stable filters (assuming numerical errors
   don't spoil that).  SILK's implementation of Burg's method is also
   computationally faster than the autocovariance method.  The
   implementation of Burg's method differs from traditional
   implementations in two aspects.  The first difference is that it
   operates on autocorrelations, similar to the Schur algorithm [SCHUR],
   but with a simple update to the autocorrelations after finding each
   reflection coefficient to make the result identical to Burg's method.
   This brings down the complexity of Burg's method to near that of the
   autocorrelation method.  The second difference is that the signal in
   each subframe is scaled by the inverse of the residual quantization
   step size.  Subframes with a small quantization step size will, on
   average, spend more bits for a given amount of residual energy than
   subframes with a large step size.  Without scaling, Burg's method
   minimizes the total residual energy in all subframes, which doesn't
   necessarily minimize the total number of bits needed for coding the
   quantized residual.  The residual energy of the scaled subframes is a
   better measure for that number of bits.

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5.2.3.5.  LSF Quantization

   Unlike many other speech codecs, SILK uses variable bitrate coding
   for the LSFs.  This improves the average rate-distortion (R-D) trade-
   off and reduces outliers.  The variable bitrate coding minimizes a
   linear combination of the weighted quantization errors and the
   bitrate.  The weights for the quantization errors are the Inverse
   Harmonic Mean Weighting (IHMW) function proposed by Laroia et al.
   (see [LAROIA-ICASSP]).  These weights are referred to here as Laroia
   weights.

   The LSF quantizer consists of two stages.  The first stage is an
   (unweighted) vector quantizer (VQ), with a codebook size of 32
   vectors.  The quantization errors for the codebook vector are sorted,
   and for the N best vectors a second stage quantizer is run.  By
   varying the number N, a trade-off is made between R-D performance and
   computational efficiency.  For each of the N codebook vectors, the
   Laroia weights corresponding to that vector (and not to the input
   vector) are calculated.  Then, the residual between the input LSF
   vector and the codebook vector is scaled by the square roots of these
   Laroia weights.  This scaling partially normalizes error sensitivity
   for the residual vector so that a uniform quantizer with fixed step
   sizes can be used in the second stage without too much performance
   loss.  Additionally, by scaling with Laroia weights determined from
   the first-stage codebook vector, the process can be reversed in the
   decoder.

   The second stage uses predictive delayed decision scalar
   quantization.  The quantization error is weighted by Laroia weights
   determined from the LSF input vector.  The predictor multiplies the
   previous quantized residual value by a prediction coefficient that
   depends on the vector index from the first stage VQ and on the
   location in the LSF vector.  The prediction is subtracted from the
   LSF residual value before quantizing the result and is added back
   afterwards.  This subtraction can be interpreted as shifting the
   quantization levels of the scalar quantizer, and as a result the
   quantization error of each value depends on the quantization decision
   of the previous value.  This dependency is exploited by the delayed
   decision mechanism to search for a quantization sequency with best
   R-D performance with a Viterbi-like algorithm [VITERBI].  The
   quantizer processes the residual LSF vector in reverse order (i.e.,
   it starts with the highest residual LSF value).  This is done because
   the prediction works slightly better in the reverse direction.

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   The quantization index of the first stage is entropy coded.  The
   quantization sequence from the second stage is also entropy coded,
   where for each element the probability table is chosen depending on
   the vector index from the first stage and the location of that
   element in the LSF vector.

5.2.3.5.1.  LSF Stabilization

   If the input is stable, finding the best candidate usually results in
   a quantized vector that is also stable.  Because of the two-stage
   approach, however, it is possible that the best quantization
   candidate is unstable.  The encoder applies the same stabilization
   procedure applied by the decoder (see Section 4.2.7.5.4) to ensure
   the LSF parameters are within their valid range, increasingly sorted,
   and have minimum distances between each other and the border values.

5.2.3.6.  LTP Quantization

   For voiced frames, the prediction analysis described in
   Section 5.2.3.4.1 resulted in four sets (one set per subframe) of
   five LTP coefficients, plus four weighting matrices.  The LTP
   coefficients for each subframe are quantized using entropy
   constrained vector quantization.  A total of three vector codebooks
   are available for quantization, with different rate-distortion trade-
   offs.  The three codebooks have 10, 20, and 40 vectors and average
   rates of about 3, 4, and 5 bits per vector, respectively.
   Consequently, the first codebook has larger average quantization
   distortion at a lower rate, whereas the last codebook has smaller
   average quantization distortion at a higher rate.  Given the
   weighting matrix W_ltp and LTP vector b, the weighted rate-distortion
   measure for a codebook vector cb_i with rate r_i is give by

               RD = u * (b - cb_i)' * W_ltp * (b - cb_i) + r_i

   where u is a fixed, heuristically determined parameter balancing the
   distortion and rate.  Which codebook gives the best performance for a
   given LTP vector depends on the weighting matrix for that LTP vector.
   For example, for a low valued W_ltp, it is advantageous to use the
   codebook with 10 vectors as it has a lower average rate.  For a large
   W_ltp, on the other hand, it is often better to use the codebook with
   40 vectors, as it is more likely to contain the best codebook vector.
   The weighting matrix W_ltp depends mostly on two aspects of the input
   signal.  The first is the periodicity of the signal; the more
   periodic, the larger W_ltp.  The second is the change in signal
   energy in the current subframe, relative to the signal one pitch lag
   earlier.  A decaying energy leads to a larger W_ltp than an
   increasing energy.  Both aspects fluctuate relatively slowly, which
   causes the W_ltp matrices for different subframes of one frame often

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   to be similar.  Because of this, one of the three codebooks typically
   gives good performance for all subframes.  Therefore, the codebook
   search for the subframe LTP vectors is constrained to only allow
   codebook vectors to be chosen from the same codebook, resulting in a
   rate reduction.

   To find the best codebook, each of the three vector codebooks is used
   to quantize all subframe LTP vectors and produce a combined weighted
   rate-distortion measure for each vector codebook.  The vector
   codebook with the lowest combined rate-distortion over all subframes
   is chosen.  The quantized LTP vectors are used in the noise shaping
   quantizer, and the index of the codebook plus the four indices for
   the four subframe codebook vectors are passed on to the range
   encoder.

5.2.3.7.  Pre-filter

   In the pre-filter, the input signal is filtered using the spectral
   valley de-emphasis filter coefficients from the noise shaping
   analysis (see Section 5.2.3.3).  By applying only the noise shaping
   analysis filter to the input signal, it provides the input to the
   noise shaping quantizer.

5.2.3.8.  Noise Shaping Quantizer

   The noise shaping quantizer independently shapes the signal and
   coding noise spectra to obtain a perceptually higher quality at the
   same bitrate.

   The pre-filter output signal is multiplied with a compensation gain G
   computed in the noise shaping analysis.  Then, the output of a
   synthesis shaping filter is added, and the output of a prediction
   filter is subtracted to create a residual signal.  The residual
   signal is multiplied by the inverse quantized quantization gain from
   the noise shaping analysis and input to a scalar quantizer.  The
   quantization indices of the scalar quantizer represent a signal of
   pulses that is input to the pyramid range encoder.  The scalar
   quantizer also outputs a quantization signal, which is multiplied by
   the quantized quantization gain from the noise shaping analysis to
   create an excitation signal.  The output of the prediction filter is
   added to the excitation signal to form the quantized output signal
   y(n).  The quantized output signal y(n) is input to the synthesis
   shaping and prediction filters.

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   Optionally, the noise shaping quantizer operates in a delayed
   decision mode.  In this mode, it uses a Viterbi algorithm to keep
   track of multiple rounding choices in the quantizer and select the
   best one after a delay of 32 samples.  This improves the rate/
   distortion performance of the quantizer.

5.2.3.9.  Constant Bitrate Mode

   SILK was designed to run in variable bitrate (VBR) mode.  However,
   the reference implementation also has a constant bitrate (CBR) mode
   for SILK.  In CBR mode, SILK will attempt to encode each packet with
   no more than the allowed number of bits.  The Opus wrapper code then
   pads the bitstream if any unused bits are left in SILK mode, or it
   encodes the high band with the remaining number of bits in Hybrid
   mode.  The number of payload bits is adjusted by changing the
   quantization gains and the rate/distortion trade-off in the noise
   shaping quantizer, in an iterative loop around the noise shaping
   quantizer and entropy coding.  Compared to the SILK VBR mode, the CBR
   mode has lower audio quality at a given average bitrate and has
   higher computational complexity.

5.3.  CELT Encoder

   Most of the aspects of the CELT encoder can be directly derived from
   the description of the decoder.  For example, the filters and
   rotations in the encoder are simply the inverse of the operation
   performed by the decoder.  Similarly, the quantizers generally
   optimize for the mean square error (because noise shaping is part of
   the bitstream itself), so no special search is required.  For this
   reason, only the less straightforward aspects of the encoder are
   described here.

5.3.1.  Pitch Pre-filter

   The pitch pre-filter is applied after the pre-emphasis.  It is
   applied in such a way as to be the inverse of the decoder's post-
   filter.  The main non-obvious aspect of the pre-filter is the
   selection of the pitch period.  The pitch search should be optimized
   for the following criteria:

   o  continuity: it is important that the pitch period does not change
      abruptly between frames; and

   o  avoidance of pitch multiples: when the period used is a multiple
      of the real period (lower frequency fundamental), the post-filter
      loses most of its ability to reduce noise

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5.3.2.  Bands and Normalization

   The MDCT output is divided into bands that are designed to match the
   ear's critical bands for the smallest (2.5 ms) frame size.  The
   larger frame sizes use integer multiples of the 2.5 ms layout.  For
   each band, the encoder computes the energy that will later be
   encoded.  Each band is then normalized by the square root of the
   *unquantized* energy, such that each band now forms a unit vector X.
   The energy and the normalization are computed by
   compute_band_energies() and normalise_bands() (bands.c),
   respectively.

5.3.3.  Energy Envelope Quantization

   Energy quantization (both coarse and fine) can be easily understood
   from the decoding process.  For all useful bitrates, the coarse
   quantizer always chooses the quantized log energy value that
   minimizes the error for each band.  Only at very low rate does the
   encoder allow larger errors to minimize the rate and avoid using more
   bits than are available.  When the available CPU requirements allow
   it, it is best to try encoding the coarse energy both with and
   without inter-frame prediction such that the best prediction mode can
   be selected.  The optimal mode depends on the coding rate, the
   available bitrate, and the current rate of packet loss.

   The fine energy quantizer always chooses the quantized log energy
   value that minimizes the error for each band because the rate of the
   fine quantization depends only on the bit allocation and not on the
   values that are coded.

5.3.4.  Bit Allocation

   The encoder must use exactly the same bit allocation process as used
   by the decoder and described in Section 4.3.3.  The three mechanisms
   that can be used by the encoder to adjust the bitrate on a frame-by-
   frame basis are band boost, allocation trim, and band skipping.

5.3.4.1.  Band Boost

   The reference encoder makes a decision to boost a band when the
   energy of that band is significantly higher than that of the
   neighboring bands.  Let E_j be the log-energy of band j, we define

      D_j = 2*E_j - E_j-1 - E_j+1

   The allocation of band j is boosted once if D_j > t1 and twice if D_j
   > t2.  For LM>=1, t1=2 and t2=4, while for LM<1, t1=3 and t2=5.

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5.3.4.2.  Allocation Trim

   The allocation trim is a value between 0 and 10 (inclusively) that
   controls the allocation balance between the low and high frequencies.
   The encoder starts with a safe "default" of 5 and deviates from that
   default in two different ways.  First, the trim can deviate by +/- 2
   depending on the spectral tilt of the input signal.  For signals with
   more low frequencies, the trim is increased by up to 2, while for
   signals with more high frequencies, the trim is decreased by up to 2.
   For stereo inputs, the trim value can be decreased by up to 4 when
   the inter-channel correlation at low frequency (first 8 bands) is
   high.

5.3.4.3.  Band Skipping

   The encoder uses band skipping to ensure that the shape of the bands
   is only coded if there is at least 1/2 bit per sample available for
   the PVQ.  If not, then no bit is allocated and folding is used
   instead.  To ensure continuity in the allocation, some amount of
   hysteresis is added to the process, such that a band that received
   PVQ bits in the previous frame only needs 7/16 bit/sample to be coded
   for the current frame, while a band that did not receive PVQ bits in
   the previous frames needs at least 9/16 bit/sample to be coded.

5.3.5.  Stereo Decisions

   Because CELT applies mid-side stereo coupling in the normalized
   domain, it does not suffer from important stereo image problems even
   when the two channels are completely uncorrelated.  For this reason,
   it is always safe to use stereo coupling on any audio frame.  That
   being said, there are some frames for which dual (independent) stereo
   is still more efficient.  This decision is made by comparing the
   estimated entropy with and without coupling over the first 13 bands,
   taking into account the fact that all bands with more than two MDCT
   bins require one extra degree of freedom when coded in mid-side.  Let
   L1_ms and L1_lr be the L1-norm of the mid-side vector and the L1-norm
   of the left-right vector, respectively.  The decision to use mid-side
   is made if and only if

                            L1_ms          L1_lr
                           --------    <   -----
                           bins + E        bins

   where bins is the number of MDCT bins in the first 13 bands and E is
   the number of extra degrees of freedom for mid-side coding.  For
   LM>1, E=13, otherwise E=5.

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   The reference encoder decides on the intensity stereo threshold based
   on the bitrate alone.  After taking into account the frame size by
   subtracting 80 bits per frame for coarse energy, the first band using
   intensity coding is as follows:

                     +------------------+------------+
                     | bitrate (kbit/s) | start band |
                     +------------------+------------+
                     |        <35       |      8     |
                     |                  |            |
                     |       35-50      |     12     |
                     |                  |            |
                     |       50-68      |     16     |
                     |                  |            |
                     |       84-84      |     18     |
                     |                  |            |
                     |      84-102      |     19     |
                     |                  |            |
                     |      102-130     |     20     |
                     |                  |            |
                     |       >130       |  disabled  |
                     +------------------+------------+

                 Table 66: Thresholds for Intensity Stereo

5.3.6.  Time-Frequency Decision

   The choice of time-frequency resolution used in Section 4.3.4.5 is
   based on R-D optimization.  The distortion is the L1-norm (sum of
   absolute values) of each band after each TF resolution under
   consideration.  The L1 norm is used because it represents the entropy
   for a Laplacian source.  The number of bits required to code a change
   in TF resolution between two bands is higher than the cost of having
   those two bands use the same resolution, which is what requires the
   R-D optimization.  The optimal decision is computed using the Viterbi
   algorithm.  See tf_analysis() in celt/celt.c.

5.3.7.  Spreading Values Decision

   The choice of the spreading value in Table 59 has an impact on the
   nature of the coding noise introduced by CELT.  The larger the f_r
   value, the lower the impact of the rotation, and the more tonal the
   coding noise.  The more tonal the signal, the more tonal the noise
   should be, so the CELT encoder determines the optimal value for f_r
   by estimating how tonal the signal is.  The tonality estimate is
   based on discrete pdf (4-bin histogram) of each band.  Bands that

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   have a large number of small values are considered more tonal and a
   decision is made by combining all bands with more than 8 samples.
   See spreading_decision() in celt/bands.c.

5.3.8.  Spherical Vector Quantization

   CELT uses a Pyramid Vector Quantizer (PVQ) [PVQ] for quantizing the
   details of the spectrum in each band that have not been predicted by
   the pitch predictor.  The PVQ codebook consists of all sums of K
   signed pulses in a vector of N samples, where two pulses at the same
   position are required to have the same sign.  Thus, the codebook
   includes all integer codevectors y of N dimensions that satisfy
   sum(abs(y(j))) = K.

   In bands where there are sufficient bits allocated, PVQ is used to
   encode the unit vector that results from the normalization in
   Section 5.3.2 directly.  Given a PVQ codevector y, the unit vector X
   is obtained as X = y/||y||, where ||.|| denotes the L2 norm.

5.3.8.1.  PVQ Search

   The search for the best codevector y is performed by alg_quant()
   (vq.c).  There are several possible approaches to the search, with a
   trade-off between quality and complexity.  The method used in the
   reference implementation computes an initial codeword y1 by
   projecting the normalized spectrum X onto the codebook pyramid of K-1
   pulses:

   y0 = truncate_towards_zero( (K-1) * X / sum(abs(X)))

   Depending on N, K and the input data, the initial codeword y0 may
   contain from 0 to K-1 non-zero values.  All the remaining pulses,
   with the exception of the last one, are found iteratively with a
   greedy search that minimizes the normalized correlation between y and
   X:

                                   T
                             J = -X * y / ||y||

   The search described above is considered to be a good trade-off
   between quality and computational cost.  However, there are other
   possible ways to search the PVQ codebook and the implementers MAY use
   any other search methods.  See alg_quant() in celt/vq.c.

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5.3.8.2.  PVQ Encoding

   The vector to encode, X, is converted into an index i such that
   0 <= i < V(N,K) as follows.  Let i = 0 and k = 0.  Then, for
   j = (N - 1) down to 0, inclusive, do:

   1.  If k > 0, set i = i + (V(N-j-1,k-1) + V(N-j,k-1))/2.

   2.  Set k = k + abs(X[j]).

   3.  If X[j] < 0, set i = i + (V(N-j-1,k) + V(N-j,k))/2.

   The index i is then encoded using the procedure in Section 5.1.4 with
   ft = V(N,K).

6.  Conformance

   It is our intention to allow the greatest possible choice of freedom
   in implementing the specification.  For this reason, outside of the
   exceptions noted in this section, conformance is defined through the
   reference implementation of the decoder provided in Appendix A.
   Although this document includes a prose description of the codec,
   should the description contradict the source code of the reference
   implementation, the latter shall take precedence.

   Compliance with this specification means that, in addition to
   following the normative keywords in this document, a decoder's output
   MUST also be within the thresholds specified by the opus_compare.c
   tool (included with the code) when compared to the reference
   implementation for each of the test vectors provided (see
   Appendix A.4) and for each output sampling rate and channel count
   supported.  In addition, a compliant decoder implementation MUST have
   the same final range decoder state as that of the reference decoder.
   It is therefore RECOMMENDED that the decoder implement the same
   functional behavior as the reference.  A decoder implementation is
   not required to support all output sampling rates or all output
   channel counts.

6.1.  Testing

   Using the reference code provided in Appendix A, a test vector can be
   decoded with

      opus_demo -d <rate> <channels> testvectorX.bit testX.out

   where <rate> is the sampling rate and can be 8000, 12000, 16000,
   24000, or 48000, and <channels> is 1 for mono or 2 for stereo.

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   If the range decoder state is incorrect for one of the frames, the
   decoder will exit with "Error: Range coder state mismatch between
   encoder and decoder".  If the decoder succeeds, then the output can
   be compared with the "reference" output with

      opus_compare -s -r <rate> testvectorX.dec testX.out

   for stereo or

      opus_compare -r <rate> testvectorX.dec testX.out

   for mono.

   In addition to indicating whether the test vector comparison passes,
   the opus_compare tool outputs an "Opus quality metric" that indicates
   how well the tested decoder matches the reference implementation.  A
   quality of 0 corresponds to the passing threshold, while a quality of
   100 is the highest possible value and means that the output of the
   tested decoder is identical to the reference implementation.  The
   passing threshold (quality 0) was calibrated in such a way that it
   corresponds to additive white noise with a 48 dB SNR (similar to what
   can be obtained on a cassette deck).  It is still possible for an
   implementation to sound very good with such a low quality measure
   (e.g., if the deviation is due to inaudible phase distortion), but
   unless this is verified by listening tests, it is RECOMMENDED that
   implementations achieve a quality above 90 for 48 kHz decoding.  For
   other sampling rates, it is normal for the quality metric to be lower
   (typically, as low as 50 even for a good implementation) because of
   harmless mismatch with the delay and phase of the internal sampling
   rate conversion.

   On POSIX environments, the run_vectors.sh script can be used to
   verify all test vectors.  This can be done with

      run_vectors.sh <exec path> <vector path> <rate>

   where <exec path> is the directory where the opus_demo and
   opus_compare executables are built and <vector path> is the directory
   containing the test vectors.

6.2.  Opus Custom

   Opus Custom is an OPTIONAL part of the specification that is defined
   to handle special sample rates and frame rates that are not supported
   by the main Opus specification.  Use of Opus Custom is discouraged
   for all but very special applications for which a frame size
   different from 2.5, 5, 10, or 20 ms is needed (for either complexity
   or latency reasons).  Because Opus Custom is optional, streams

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   encoded using Opus Custom cannot be expected to be decodable by all
   Opus implementations.  Also, because no in-band mechanism exists for
   specifying the sampling rate and frame size of Opus Custom streams,
   out-of-band signaling is required.  In Opus Custom operation, only
   the CELT layer is available, using the opus_custom_* function calls
   in opus_custom.h.

7.  Security Considerations

   Like any other audio codec, Opus should not be used with insecure
   ciphers or cipher-modes that are vulnerable to known plaintext
   attacks.  In addition to the zeros used in Opus padding, digital
   silence frames generate predictable compressed results and the TOC
   byte may have an easily predictable value.

   Implementations of the Opus codec need to take appropriate security
   considerations into account, as outlined in [DOS].  It is extremely
   important for the decoder to be robust against malicious payloads.
   Malicious payloads must not cause the decoder to overrun its
   allocated memory or to take an excessive amount of resources to
   decode.  Although problems in encoders are typically rarer, the same
   applies to the encoder.  Malicious audio streams must not cause the
   encoder to misbehave because this would allow an attacker to attack
   transcoding gateways.

   The reference implementation contains no known buffer overflow or
   cases where a specially crafted packet or audio segment could cause a
   significant increase in CPU load.  However, on certain CPU
   architectures where denormalized floating-point operations are much
   slower than normal floating-point operations, it is possible for some
   audio content (e.g., silence or near silence) to cause an increase in
   CPU load.  Denormals can be introduced by reordering operations in
   the compiler and depend on the target architecture, so it is
   difficult to guarantee that an implementation avoids them.  For
   architectures on which denormals are problematic, adding very small
   floating-point offsets to the affected signals to prevent significant
   numbers of denormalized operations is RECOMMENDED.  Alternatively, it
   is often possible to configure the hardware to treat denormals as
   zero (DAZ).  No such issue exists for the fixed-point reference
   implementation.

   The reference implementation was validated in the following
   conditions:

   1.  Sending the decoder valid packets generated by the reference
       encoder and verifying that the decoder's final range coder state
       matches that of the encoder.

Valin, et al.                Standards Track                  [Page 157]
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   2.  Sending the decoder packets generated by the reference encoder
       and then subjected to random corruption.

   3.  Sending the decoder random packets.

   4.  Sending the decoder packets generated by a version of the
       reference encoder modified to make random coding decisions
       (internal fuzzing), including mode switching, and verifying that
       the range coder final states match.

   In all of the conditions above, both the encoder and the decoder were
   run inside the Valgrind [VALGRIND] memory debugger, which tracks
   reads and writes to invalid memory regions as well as the use of
   uninitialized memory.  There were no errors reported on any of the
   tested conditions.

8.  Acknowledgements

   Thanks to all other developers, including Henrik Astrom, Jon
   Bergenheim, Raymond Chen, Soren Skak Jensen, Gregory Maxwell,
   Christopher Montgomery, and Karsten Vandborg Sorensen.  We would also
   like to thank Igor Dyakonov, Hoang Thi Minh Nguyet, Christian Hoene,
   Gian-Carlo Pascutto, and Jan Skoglund for their help with testing of
   the Opus codec.  Thanks to Andrew D'Addesio, Elwyn Davies, Ralph
   Giles, John Ridges, Ben Schwartz, Kat Walsh, Mark Warner, Keith Yan,
   and many others on the Opus and CELT mailing lists for their bug
   reports and feedback.  At last, the authors would like to thank
   Robert Sparks, Cullen Jennings, and Jonathan Rosenberg for their
   support throughout the standardization process.

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9.  References

9.1.  Normative References

   [RFC2119]  Bradner, S., "Key words for use in RFCs to Indicate
              Requirement Levels", BCP 14, RFC 2119, March 1997.

9.2.  Informative References

   [BURG]     Burg, J., "Maximum Entropy Spectral Analysis", Proceedings
              of the 37th Annual International SEG Meeting, Vol.
              6, 1975.

   [CELT]     Valin, JM., Terriberry, T., Maxwell, G., and C.
              Montgomery, "Constrained-Energy Lapped Transform (CELT)
              Codec", Work in Progress, July 2010.

   [CODING-THESIS]
              Pasco, R., "Source coding algorithms for fast data
              compression", Ph.D. thesis Dept. of Electrical
              Engineering, Stanford University, May 1976.

   [DOS]      Handley, M., Rescorla, E., and IAB, "Internet Denial-of-
              Service Considerations", RFC 4732, December 2006.

   [FFT]      Wikipedia, "Fast Fourier Transform",
              <http://en.wikipedia.org/w/
              index.php?title=Fast_Fourier_transform&oldid=508004516>.

   [GOOGLE-NETEQ]
              "Google NetEQ code", <http://code.google.com/p/webrtc/
              source/browse/trunk/src/modules/audio_coding/NetEQ/main/
              source/?r=583>.

   [GOOGLE-WEBRTC]
              "Google WebRTC code", <http://code.google.com/p/webrtc/>.

   [HADAMARD] Wikipedia, "Hadamard Transform", <http://en.wikipedia.org/
              w/index.php?title=Hadamard_transform&oldid=508252957>.

   [KABAL86]  Kabal, P. and R. Ramachandran, "The Computation of Line
              Spectral Frequencies Using Chebyshev Polynomials", IEEE
              Trans. Acoustics, Speech, Signal Processing, Vol. 34, no.
              6, pp. 1419-1426, December 1986.

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RFC 6716                 Interactive Audio Codec          September 2012

   [LAROIA-ICASSP]
              Laroia, R., Phamdo, N., and N. Farvardin, "Robust and
              Efficient Quantization of Speech LSP Parameters Using
              Structured Vector Quantization", ICASSP-1991, Proc. IEEE
              Int. Conf. Acoust., Speech, Signal Processing, pp. 641-
              644, October 1991.

   [LPC]      Wikipedia, "Linear Prediction", <http://en.wikipedia.org/
              w/index.php?title=Linear_prediction&oldid=497201278>.

   [MARTIN79] Martin, G., "Range encoding: An algorithm for removing
              redundancy from a digitised message", Proc. Institution of
              Electronic and Radio Engineers International Conference on
              Video and Data Recording, 1979.

   [MATROSKA-WEBSITE]
              "Matroska website", <http://matroska.org/>.

   [MDCT]     Wikipedia, "Modified Discrete Cosine Transform", <http://
              en.wikipedia.org/w/
              index.php?title=Modified_discrete_cosine_
              transform&oldid=490295438>.

   [OPUS-GIT] "Opus Git Repository", <https://git.xiph.org/opus.git>.

   [OPUS-WEBSITE]
              "Opus website", <http://opus-codec.org/>.

   [PRINCEN86]
              Princen, J. and A. Bradley, "Analysis/Synthesis Filter
              Bank Design Based on Time Domain Aliasing Cancellation",
              IEEE Trans. Acoustics, Speech, and Siginal Processing,
              ASSP-34 (5), pp. 1153-1161, October, 1986.

   [PVQ]      Fischer, T., "A Pyramid Vector Quantizer", IEEE Trans. on
              Information Theory, Vol. 32, pp. 568-583, July 1986.

   [RANGE-CODING]
              Wikipedia, "Range Coding", <http://en.wikipedia.org/w/
              index.php?title=Range_encoding&oldid=509582757>.

   [REQUIREMENTS]
              Valin, JM. and K. Vos, "Requirements for an Internet Audio
              Codec", RFC 6366, August 2011.

Valin, et al.                Standards Track                  [Page 160]
RFC 6716                 Interactive Audio Codec          September 2012

   [RFC3533]  Pfeiffer, S., "The Ogg Encapsulation Format Version 0",
              RFC 3533, May 2003.

   [RFC3550]  Schulzrinne, H., Casner, S., Frederick, R., and V.
              Jacobson, "RTP: A Transport Protocol for Real-Time
              Applications", STD 64, RFC 3550, July 2003.

   [SCHUR]    Le Roux, J. and C. Gueguen, "A fixed point computation of
              partial correlation coefficients", ICASSP-1977, Proc. IEEE
              Int. Conf. Acoustics, Speech, and Signal Processing, pp.
              257-259, June 1977.

   [SILK]     Vos, K., Jensen, S., and K. Sorensen, "SILK Speech Codec",
              Work in Progress, September 2010.

   [SPECTRAL-PAIRS]
              Wikipedia, "Line Spectral Pairs", <http://
              en.wikipedia.org/w/
              index.php?title=Line_spectral_pairs&oldid=365426016>.

   [SRTP-VBR] Perkins, C. and JM. Valin, "Guidelines for the Use of
              Variable Bit Rate Audio with Secure RTP", RFC 6562,
              March 2012.

   [VALGRIND] "Valgrind website", <http://valgrind.org/>.

   [VALIN2010]
              Valin, JM., Terriberry, T., Montgomery, C., and G.
              Maxwell, "A High-Quality Speech and Audio Codec With Less
              Than 10 ms Delay", IEEE Trans. on Audio, Speech, and
              Language Processing, Vol. 18, No. 1, pp. 58-67 2010.

   [VECTORS-PROC]
              "Opus Testvectors (proceedings)", <http://www.ietf.org/
              proceedings/83/slides/slides-83-codec-0.gz>.

   [VECTORS-WEBSITE]
              "Opus Testvectors (website)",
              <http://opus-codec.org/testvectors/>.

   [VITERBI]  Wikipedia, "Viterbi Algorithm", <http://en.wikipedia.org/
              w/index.php?title=Viterbi_algorithm&oldid=508835871>.

   [VORBIS-WEBSITE]
              "Vorbis website", <http://xiph.org/vorbis/>.

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   [WHITENING]
              Wikipedia, "White Noise", <http://en.wikipedia.org/w/
              index.php?title=White_noise&oldid=497791998>.

   [Z-TRANSFORM]
              Wikipedia, "Z-transform", <http://en.wikipedia.org/w/
              index.php?title=Z-transform&oldid=508392884>.

   [ZWICKER61]
              Zwicker, E., "Subdivision of the Audible Frequency Range
              into Critical Bands", The Journal of the Acoustical
              Society of America, Vol. 33, No 2 pp. 248, February 1961.

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Appendix A.  Reference Implementation

   This appendix contains the complete source code for the reference
   implementation of the Opus codec written in C.  By default, this
   implementation relies on floating-point arithmetic, but it can be
   compiled to use only fixed-point arithmetic by defining the
   FIXED_POINT macro.  The normative behavior is defined as the output
   using the floating-point configuration.  Information on building and
   using the reference implementation is available in the README file.

   The implementation can be compiled with either a C89 or a C99
   compiler.  It is reasonably optimized for most platforms such that
   only architecture-specific optimizations are likely to be useful.
   The Fast Fourier Transform (FFT) [FFT] used is a slightly modified
   version of the KISS-FFT library, but it is easy to substitute any
   other FFT library.

   While the reference implementation does not rely on any _undefined
   behavior_ as defined by C89 or C99, it relies on common
   _implementation-defined behavior_ for two's complement architectures:

   o  Right shifts of negative values are consistent with two's
      complement arithmetic, so that a>>b is equivalent to
      floor(a/(2**b)),

   o  For conversion to a signed integer of N bits, the value is reduced
      modulo 2**N to be within range of the type,

   o  The result of integer division of a negative value is truncated
      towards zero, and

   o  The compiler provides a 64-bit integer type (a C99 requirement
      which is supported by most C89 compilers).

   In its current form, the reference implementation also requires the
   following architectural characteristics to obtain acceptable
   performance:

   o  Two's complement arithmetic,

   o  At least a 16 bit by 16 bit integer multiplier (32-bit result),
      and

   o  At least a 32-bit adder/accumulator.

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A.1.  Extracting the Source

   The complete source code can be extracted from this document, by
   running the following command line:

   o  cat rfc6716.txt | grep '^\ \ \ ###' | sed -e 's/...###//' | base64
      --decode > opus-rfc6716.tar.gz

   o  tar xzvf opus-rfc6716.tar.gz

   o  cd opus-rfc6716

   o  make

   On systems where the provided Makefile does not work, the following
   command line may be used to compile the source code:

   o  cc -O2 -g -o opus_demo src/opus_demo.c `cat *.mk | grep -v fixed |
      sed -e 's/.*=//' -e 's/\\\\//'` -DOPUS_BUILD -Iinclude -Icelt
      -Isilk -Isilk/float -DUSE_ALLOCA -Drestrict= -lm

   On systems where the base64 utility is not present, the following
   commands can be used instead:

   o  cat rfc6716.txt | grep '^\ \ \ ###' | sed -e 's/...###//' >
      opus.b64

   o  openssl base64 -d -in opus.b64 > opus-rfc6716.tar.gz

   The SHA1 hash of the opus-rfc6716.tar.gz file is
   86a927223e73d2476646a1b933fcd3fffb6ecc8c.

A.2.  Up-to-Date Implementation

   As of the time of publication of this memo, an up-to-date
   implementation conforming to this RFC is available in a Git
   repository [OPUS-GIT].  Releases and other resources are available at
   [OPUS-WEBSITE].  However, although that implementation is expected to
   remain conformant with the RFC, it is the code in this document that
   shall remain normative.

A.3.  Base64-Encoded Source Code

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   ###EFuhCqoyvIShF/pBGT5ai1ml503LoH1+WDBoW3MrYOMy9MzA8C2zXICcz9+Z4Rx2

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Valin, et al.                Standards Track                  [Page 166]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 167]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 168]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 169]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 170]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 171]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 172]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 173]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 174]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 175]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 176]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 177]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 178]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 179]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 180]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 181]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 182]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 183]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 184]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 185]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 186]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 187]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 188]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 189]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 190]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 191]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 192]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 193]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 194]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 195]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 196]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 197]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 198]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 199]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 200]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 201]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 202]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 203]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 204]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 205]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 206]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 207]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 208]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 209]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 210]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 211]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 212]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 213]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 214]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 215]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 216]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 217]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 218]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 219]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 220]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 221]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 222]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 223]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 224]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 225]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 226]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 227]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 228]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 229]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 230]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 231]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 232]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 233]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 234]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 235]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 236]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 237]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 238]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 239]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 240]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 241]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 242]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 243]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 244]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 245]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 246]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 247]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 248]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 249]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 250]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 251]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 252]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 253]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 254]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 255]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 256]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 257]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 258]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 259]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 260]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 261]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 262]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 263]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 264]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 265]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 266]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 267]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 268]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 269]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 270]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 271]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 272]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 273]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 274]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 275]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 276]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 277]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 278]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 279]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 280]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 281]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 282]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 283]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 284]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 285]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 286]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 287]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 288]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 289]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 290]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 291]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 292]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 293]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 294]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 295]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 296]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 297]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 298]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 299]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 300]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 301]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 302]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 303]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 304]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 305]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 306]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 307]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 308]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 309]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 310]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 311]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 312]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 313]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 314]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 315]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 316]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 317]
RFC 6716                 Interactive Audio Codec          September 2012

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Valin, et al.                Standards Track                  [Page 318]
RFC 6716                 Interactive Audio Codec          September 2012

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A.4.  Test Vectors

   Because of size constraints, the Opus test vectors are not
   distributed in this document.  They are available in the proceedings
   of the 83rd IETF meeting (Paris) [VECTORS-PROC] and from the Opus
   codec website at [VECTORS-WEBSITE].  These test vectors were created
   specifically to exercise all aspects of the decoder.  Therefore, the
   audio quality of the decoded output is significantly lower than what
   Opus can achieve in normal operation.

   The SHA1 hash of the files in the test vector package are

   e49b2862ceec7324790ed8019eb9744596d5be01  testvector01.bit
   b809795ae1bcd606049d76de4ad24236257135e0  testvector02.bit
   e0c4ecaeab44d35a2f5b6575cd996848e5ee2acc  testvector03.bit
   a0f870cbe14ebb71fa9066ef3ee96e59c9a75187  testvector04.bit
   9b3d92b48b965dfe9edf7b8a85edd4309f8cf7c8  testvector05.bit
   28e66769ab17e17f72875283c14b19690cbc4e57  testvector06.bit
   bacf467be3215fc7ec288f29e2477de1192947a6  testvector07.bit
   ddbe08b688bbf934071f3893cd0030ce48dba12f  testvector08.bit
   3932d9d61944dab1201645b8eeaad595d5705ecb  testvector09.bit
   521eb2a1e0cc9c31b8b740673307c2d3b10c1900  testvector10.bit
   6bc8f3146fcb96450c901b16c3d464ccdf4d5d96  testvector11.bit
   338c3f1b4b97226bc60bc41038becbc6de06b28f  testvector12.bit
   a20a2122d42de644f94445e20185358559623a1f  testvector01.dec
   48ac1ff1995250a756e1e17bd32acefa8cd2b820  testvector02.dec
   d15567e919db2d0e818727092c0af8dd9df23c95  testvector03.dec
   1249dd28f5bd1e39a66fd6d99449dca7a8316342  testvector04.dec
   93eee37e5d26a456d2c24483060132ff7eae2143  testvector05.dec
   a294fc17e3157768c46c5ec0f2116de0d2c37ee2  testvector06.dec
   2bf550e2f072e0941438db3f338fe99444385848  testvector07.dec
   2695c1f2d1f9748ea0bf07249c70fd7b87f61680  testvector08.dec
   12862add5d53a9d2a7079340a542a2f039b992bb  testvector09.dec
   a081252bb2b1a902fdc500530891f47e2a373d84  testvector10.dec
   dfd0f844f2a42df506934fac2100a3c03beec711  testvector11.dec
   8c16b2a1fb60e3550ba165068f9d7341357fdb63  testvector12.dec

Appendix B.  Self-Delimiting Framing

   To use the internal framing described in Section 3, the decoder must
   know the total length of the Opus packet, in bytes.  This section
   describes a simple variation of that framing that can be used when
   the total length of the packet is not known.  Nothing in the encoding
   of the packet itself allows a decoder to distinguish between the
   regular, undelimited framing and the self-delimiting framing
   described in this appendix.  Which one is used and where must be

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RFC 6716                 Interactive Audio Codec          September 2012

   established by context at the transport layer.  It is RECOMMENDED
   that a transport layer choose exactly one framing scheme, rather than
   allowing an encoder to signal which one it wants to use.

   For example, although a regular Opus stream does not support more
   than two channels, a multi-channel Opus stream may be formed from
   several one- and two-channel streams.  To pack an Opus packet from
   each of these streams together in a single packet at the transport
   layer, one could use the self-delimiting framing for all but the last
   stream, and then the regular, undelimited framing for the last one.
   Reverting to the undelimited framing for the last stream saves
   overhead (because the total size of the transport-layer packet will
   still be known), and ensures that a "multi-channel" stream that only
   has a single Opus stream uses the same framing as a regular Opus
   stream does.  This avoids the need for signaling to distinguish these
   two cases.

   The self-delimiting framing is identical to the regular, undelimited
   framing from Section 3, except that each Opus packet contains one
   extra length field, encoded using the same one- or two-byte scheme
   from Section 3.2.1.  This extra length immediately precedes the
   compressed data of the first Opus frame in the packet, and is
   interpreted in the various modes as follows:

   o  Code 0 packets: It is the length of the single Opus frame (see
      Figure 25).

   o  Code 1 packets: It is the length used for both of the Opus frames
      (see Figure 26).

   o  Code 2 packets: It is the length of the second Opus frame (see
      Figure 27).

   o  CBR Code 3 packets: It is the length used for all of the Opus
      frames (see Figure 28).

   o  VBR Code 3 packets: It is the length of the last Opus frame (see
      Figure 29).

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      0                   1                   2                   3
      0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     | config  |s|0|0| N1 (1-2 bytes):                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+                               |
     |               Compressed frame 1 (N1 bytes)...                :
     :                                                               |
     |                                                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+

                 Figure 25: A Self-Delimited Code 0 Packet

      0                   1                   2                   3
      0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     | config  |s|0|1| N1 (1-2 bytes):                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+                               :
     |               Compressed frame 1 (N1 bytes)...                |
     :                               +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     |                               |                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+                               :
     |               Compressed frame 2 (N1 bytes)...                |
     :                                               +-+-+-+-+-+-+-+-+
     |                                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+

                 Figure 26: A Self-Delimited Code 1 Packet

      0                   1                   2                   3
      0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     | config  |s|1|0| N1 (1-2 bytes): N2 (1-2 bytes :               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+               :
     |               Compressed frame 1 (N1 bytes)...                |
     :                               +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     |                               |                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+                               |
     |               Compressed frame 2 (N2 bytes)...                :
     :                                                               |
     |                                                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+

                 Figure 27: A Self-Delimited Code 2 Packet

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      0                   1                   2                   3
      0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     | config  |s|1|1|0|p|     M     | Pad len (Opt) : N1 (1-2 bytes):
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     |                                                               |
     :               Compressed frame 1 (N1 bytes)...                :
     |                                                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     |                                                               |
     :               Compressed frame 2 (N1 bytes)...                :
     |                                                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     |                                                               |
     :                              ...                              :
     |                                                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     |                                                               |
     :               Compressed frame M (N1 bytes)...                :
     |                                                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     :                  Opus Padding (Optional)...                   |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+

               Figure 28: A Self-Delimited CBR Code 3 Packet

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      0                   1                   2                   3
      0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     | config  |s|1|1|1|p|     M     | Padding length (Optional)     :
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     : N1 (1-2 bytes):     ...       :     N[M-1]    |     N[M]      :
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     |                                                               |
     :               Compressed frame 1 (N1 bytes)...                :
     |                                                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     |                                                               |
     :               Compressed frame 2 (N2 bytes)...                :
     |                                                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     |                                                               |
     :                              ...                              :
     |                                                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     |                                                               |
     :              Compressed frame M (N[M] bytes)...               :
     |                                                               |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
     :                  Opus Padding (Optional)...                   |
     +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+

               Figure 29: A Self-Delimited VBR Code 3 Packet

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Authors' Addresses

   Jean-Marc Valin
   Mozilla Corporation
   650 Castro Street
   Mountain View, CA  94041
   USA

   Phone: +1 650 903-0800
   EMail: jmvalin@jmvalin.ca

   Koen Vos
   Skype Technologies S.A.
   Soder Malarstrand 43
   Stockholm,   11825
   SE

   Phone: +46 73 085 7619
   EMail: koenvos74@gmail.com

   Timothy B. Terriberry
   Mozilla Corporation
   650 Castro Street
   Mountain View, CA  94041
   USA

   Phone: +1 650 903-0800
   EMail: tterriberry@mozilla.com

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